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Патент USA US3076906

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Feb. 5, 1963
Filed May 1, 1961
2 Sheets-Sheet 1
~: '43
4 T
I53 Amplifier
' Agent
Feb. 5, 1963
Filed May 1 ,
2 Sheets-Sheet 2
l’atented Feh. 5, 1963
ized by employing a thermistor in series with the selected
zener diode.
Raymond ‘V. Smith, Los Altos, Calill, assignor to Loci:
heed Aircraft ?orporation, Burbank, Calif.
Filed May l, 1961, Ser. No. 196,646
'7 Claims. (Cl. 25tl=-207)
provide a stable, high voltage supply requiring very little
This invention relates to a voltage supply and more
stable, high voltage supply for supplying a photomultiplier
Accordingly, an object of the present invention is to
Another object of the present invention is to provide a
device the necessary discrete D.C. voltages.
Still another object of the present invention is to pro
10 vide a stable voltage supply for a photomultiplier wherein
in photomultiplier devices it is mandatory that the
the voltage is supported by a capacitor-diode network.
over~all multiplication factor be kept constant irrespec~
A further object of the present invention is to provide
tive of load or the intensity of bombardment of the
supply which has a plurality of individual power
photocathode thereof. Since the latter stages of photo
supplies connected to individual dynodes of a. photomulti
multipliers draw relatively large currents it is necessary
particularly to a voltage supply uniquely adaptable to a
photomultiplier device.
15 plier.
that these stages be supplied by a low impedance source.
A still further object of the present invention is to
The conventional method for doing this is by means of a
provide a voltage supply for a photomultiplier device
voltage divider network consisting of a plurality of series
which maintains the over-all multiplication factor or" the
connected resistors which are supplied power by a high
constant irrespective of variations of 13+
voltage D.C. source. By this method it is necessary that 20 supply voltage and
photomultiplier load.
the resistance of the resistors connected to these stages
A still further object of the present invention is to pro~
be relatively low so when varying currents are drawn, the
vide a D.C. voltage supply, ?lter and current bleeder net
change in voltage drop across the associated resistor is
wherein the voltage across each component is main
small and the voltage applied to each of these stages there—
tained at a minimum thereby minimizing component fail
fore remains relatively constant. The primary disad 25 ure.
vantage of a resistive network of this type is, with the high
voltages necessary for operation and the low network re
The speci?c nature of the invention, as well as other
objects, uses and advantages thereof, will clearly appear
from the following description and from the accompany
sistance, there is large power consumption which necessi
tates a large and frequently complex power source with
corresponding voltage control difficulties.
ing drawing in which:
FIGURE 1 is a schematic illustration of the voltage
supply and control circuit of the present invention.
FIGURES 2A, 2B and 2C are curves illustrating the
operation of the device shown in FIGURE 1.
small currents and maintains a constant over-all multi
plication factor irrespective of photomultiplier load. This 35 in FIGURE 1 is schematically illustrated the circuit
of the present invention wherein reference numeral ll gen
is accomplished by converting B+ power into AC. power
denotes the oscillator, reference numeral l2 gen
by means of an oscillator and applying the AC. power
erally denotes the D.C. voltage multiplier, reference nu—
to a diode-capacitor voltage multiplier network thereby
meral 13 generally denotes the photomultiplier device and
providing a high voltage D.C. voltage source, each stage
numeral 14 generally denotes the controllsystem.
of which has consecutive integral multiples of the oscil 40 reference
operation of the system is obtained from a
lator output voltage. The voltage multiplier network has
D.C. source denoted as 13+ and is applied to the input
a low output impedance and each stage is individually
of oscillator 11. Resistor l5 and capacitor 17 are pro
connected through a ?lter circuit to separate dynodes of
to ?lter the A.C. component which may be super
the photomultiplier. Eifective ?ltering and impedance
on the 8-}- power supply. As will hereinafter be
characteristics are realized since the cynodes at the low 45
come apparent, accurate control of the 8+ power sourc
voltage stages of the voltage multiplier network draw
is unnecessary because of the unique compatibillties of
more current than the dynodes at the high voltage stages
the DC. voltage multiplier, photomultiplier and control
where the AC. components to be ?ltered are relatively
system. it has been found that a constant photomulti
The present invention obviates the disadvantages of
these prior voltage supply devices by providing a unique
voltage supply and control system that requires rela i'vely
large and require relatively large
resistors in series with u plier multiplication factor is realized with B+ voltage
the voltage multiplier output. Control of the system is
varying from about 22 to about 35 volts. This is a high—
realized by sampling the voltage at the last dynode
ly advantageous feature since the photomultiplier may
which re?ects both variations in B+ supply voltage
then be battery operated over a relatively long period of
and photomultiplier lead. This control re?ects photo
multiplier load by sensing the current drawn by the
Gscillator 11 is of the push-pull type and includes tran
last dynode and it is therefore possible to maintain
sistor l9, transistor 21, transformer 22 including windings
a constant over-all photomultiplier multiplication factor
23, 2d- and 25, and is controlled by transistor 27. Upon
the initial application of B+ power to the oscillator in
by varying the relative potentials between individual dy—
nodes as a function of photomultiplier load. The last
dynode potential is applied to a zener diode which is con
nected to a transistor for controlling the series impedance
between the 13+ supply and the input to the oscillator,
to maintain the dynode at the breakdown voltage of the
selected zener diode. Temperature compensated is real
put, either transistor 19 or transistor 21 will conduct more
rapidly than the other since two transistors are never en
tirely symmetric. Assuming transistor 19 conducts more
rapidly than transistor 21, then the rate of change of cur
rent from point “d” to point “e” is greater than from
point “d” to point “0” of winding 24. Point “0” will thus
become positive with relation to point “e,” as illustrated,
since voltage drop is proportional to rate of current change
across an inductive load.
Winding‘ 25 is wound with re
lation to winding 24 so the ?ux induced by increasing rate
of current ?ow from point “d” to point “1:” causes point
“It” to be positive with relation to point “f” of winding 25.
Since point “h” is driven positive, transistor 19 will be
driven to greater conduction and since point “f” is driven
negative, transistor 21 will be driven to lesser conduction.
this initial charge on capacitor 29 and no current will pass
through diode 41 when the anode thereof is negative with
respect to ground. Therefore, the oscillator input to ca
pacitor 29 is superposed on the negative charge thereon
‘with a resultant signal varying from ground to —200 volts
at point “m” of FIGURE 1. Since the anode of diode 42 is
positive with respect to point “m” there is ?ow of electrons
to capacitor 67 with a resultant steady state voltage at point
“0” of -—200 volts. The potential applied to capacitor
36, which is analogous to capacitor 29, varies from 0 to
of current from point “d” to point “e” is positive, and as
—-200 volts (point “m”) and the potential applied to the
the base of transistor 19 ‘is driven more positive and
cathode of diode 43, which is analogous to diode 41, is
reaches saturation, ‘the rate of change of current from
—200 volts (point “o”). In the same manner as de
point “d” to point “e” reverses. With this reversal of
scribed with relation to capacitor 29 and diode (t3, the
rate of current change, the ?ux induced in winding 25 is
reversed and point “f” will be driven positive with relation 15 potential at point “p‘” will vary between —200 and -4G0
volts. The potential at point “r” will realize a steady
to point “It.” As this occurs, transistor 21 will become
state value of ——4G() volts in the same manner as was de—
conducting and transistor 19 will become nonconducting
scribed with relation to diode 42 and capacitor 67. This
and point “e” will become positive with relation to point
same process is continued through capacitorsv 31 through
“0.” i As transistor 21 reaches saturation, the rate of
change of current from point “d” to point “c” reverses 20 41}, diodes 44 through 64 and capacitors as through '73 so
Considering only transistor 19, initially the rate of change
and point “It” becomes positive ‘with relation to point “f.”
Therefore, transistor 19 becomes conducting and transistor
21 nonconducting and the above described sequences will
be repeated. Therefore, there is free running oscillation
at a frequency ‘which is established by the oscillator param~
eters. It should be noted that when the base currents of
transistors 19 and 21 are large, the‘ transistors will not
saturate untilthe collectors approach ground potential.
the steady state potentials applied to the dynodes of photo
multiplier 13 are multiples of 200 volts, and the photo
cathode thereof is at a potential of .-2,400 volts‘
It is to be understood that various numbers of'multipli
cation stages, and various values of voltagesper stage,
may be used in particular applications, and the .twelve'sta'ge
voltage multiplier shown in FIGURE 1 is consideredito
be only exemplary.
Fhotomultiplier 13 includes photocathode’ 120 which
However, when thebase currents are small, the transistors
will saturate prior to the collectors reachingv ground po 30 emits electrons when light impinges thereupon. The num-'
ber of electrons emitted are relatively few and are ac
tential. These base currents are controlled by the ef
celerated by the ?eld created by the diiferential potential
fective collector-emitter resistance of transistor 27 the
between photocathode 12d and'grid’ 121. Dynode 122
operation of which will hereinafter be described. ‘ There
further accelerates and attracts these electrons and upon
fore, by varying these base currents, ‘the peak to eak
voltage in winding 24 is varied and as a result the peak 35 their collision therewith results in the release of a greater
number of electrons which is some multiple of the num
to peak voltage or amplitude of the signal induced in
ber of colliding electrons. This multiplicationv of elec
winding23 is varied.
trons is continued by the remaining dynodes. Assuming
In FIGURE 2A are shown the voltage signals at the
an individual dynode multiplication factor of .four and
various points indicated in FIGURE 1 during that period
when large base currents are permitted to be drawn by 40 that ten dynodes are employed, as shown, there is an over
all current or electron multiplication factor of 41° or ap-'
transistors 19 and 21. In FIGURE 2B are shown the
proximately one million. It can therefore be seen the
voltage signals at the same points when large base currents
current drawn from voltage supply 12 by dynodes 122
are not permitted to be drawn by these transistors.
through 131 progressively increases and dynode'131 draws‘
Curves A and B of FIGURE 2C represent the voltage in
duced in winding 23 during the operating conditions shown 45 very large current as compared with dynode 122', photo-'
cathode 121} or grid 121.
in FIGURE 2A and 213, respectively. Winding 23 may
As previously‘ indicated, in photomultiplier devices it is
have the polarity indicated or it may be‘ reversed by re
necessary that the over-all multiplicationfactor of‘ the
versal of the direction of winding on the associated core.
photomultiplier be kept constant irrespective of load or
It should be noted the maximum peak-to-peak amplitude
of the signals at points “c” and “e” is limited by the 50 the intensity of bombardment of the photocath‘ode there-v
of. Since the latter stages of the photomultiplier draw
15+ voltage and will have a maximum amplitude of ap
relatively large currents it is necessary that a low imped
ance source supply these stages; As previously indicated,
the conventional method for doing this is by means of a
However, the turn ratio is selected so slightly more than 55 voltage divider network consisting of a plurality of series
connected resistors which are connected to a high voltage
200 volts peak-to-peak may be obtained with about 22
D.C. source. However, it is necessary that the resistance
volts 3-]- power and still realize the necessary current for
of the resistors ‘connected to the latter dynodes be rela
successful operation. It is to be understood that various
tively low so when varying currents are drawn by these
turn ratios and 13+ voltages may be employed to pro
vide sufficient voltage and current to the particular load 60 dynodes the change in voltage drop is small and the volt
age on each dynode therefore remains relatively constant‘
which is being supplied by DC. voltage multiplier 12. It
irrespective of the variation of current. In order that ap-'‘
is also to be understood that other types of oscillators
proximately uniform voltage division be obtained, it is.
may be employed so long as they remain compatible
necessary that the over-all resistance of the network be
with the hereinafter described DC. voltage multiplier and
65 relatively low. In view of the low resistance network and
control system.
the high voltages necessary for operation, it can be seen
The output of winding 23 of oscillator 11 is applied to the
there is large power consumption which necessitates a
input of DC. voltage multiplier 12 which includes capaci
large and frequently complex power source with corre
tors 29 through 40, diodes 41 through 64, capacitors 67
proximately twice the B+ potential. Consequently, for
a predetermined‘ turn ratio between windings 23 and 24,
the induced voltage in winding 23 is likewise limited.
spondv'my voltage control difficulties.
through 78, resistors 80 through 91, resistors 93 through
104, capacitors 105 through 116 and capacitors 118 and 70 It should be particularly noted that an.A.C. signal, at.
a frequency coresponding to the oscillator frequency, is
119. Assuming the peak-to-peak voltage output of the
superposed on the DC. potential of capacitors 67 through
oscillator isfrom +100 to -—100 volts, then capacitor 29
78. This A.C. component at point “0” of voltage multi-p
will initially charge to ---100 volts since diode 41 permits
plier 12 is relatively small; however, this small A.C.
electrons to pass only in the direction to bring about‘ this
negative charge. A steady state condition is realized after 75 component is ampli?ed by the stages of the DC. voltage -
multiplier and at point “s” the A.C. component will be
relatively large. It is desirable to ?lter the A.C. compo
nent from voltage applied to the dynodes by means of
resistors 93 through 104 and capacitors 105 through 116.
Since the A.C. components at points “s” and “t” are
would be reduced. However, capacitors 67 through 78
would not rapidly follow this reduced voltage since the
current drawn therefrom would be negligible. To pro
vide rapid control, resistors 80 through 91 are provided
to discharge capacitors 67 through 78 to ground. The
values of resistors 80 through 91 are selected so the
large, it is necessary that resistors 1M and 192 have
large values of resistance and since the A.C. component
current discharged from each of capacitors 67 through
at points “0” and “r” are relatively small, the resistance
78 is uniform. This is accomplished by series connecting
of resistors 93 and 94 may be relatively small. It can
therefore be seen that voltage multiplier 12 is uniquely 10 these resistors to ground so the etfective resistance is
large at the photocathode end and small at the anode end.
adaptable to a photomultiplier tube since at the photo
This same uniform discharge rate could be accomplished
cathode end, the dynode current is small and it is possible
by connecting each of resistors 81 through 91 directly to
to employ a large resistor in series with the voltage sup
and increasing the value of each to correspond
ply to ?lter the large A.C. component; whereas, at the
the e?ective resistance of the series string. However,
anode end, where the dynodes draw large currents, the 15 with
this latter method has the disadvantage of having the
A.C. component may be etfectively ?ltered by a small
stage voltage across each resistor and consequently
resistor. Consequently, over-all e?ective ?ltering is ob
resistor failure would more readily occur.
tained and the voltage on each dynode remains relatively
The primary purpose of a photomultiplier control sys
constant irrespective of load since the source impedance
is to maintain a constant over-all multiplication
is small for dynodes drawing large currents and large
factor which is independent of dynode load or light energy
for dynodes drawing small currents.
input to the photocathode, and B+ voltage. As previ
It should be particularly noted that the capacitance of
ously indicated, in prior systems this control has been
capacitor 116 could be decreased to a value equivalent
by regulating the power supply by the volt
to the total series capacitance of capacitors 105 through
age across a shunting resistor in parallel with the resist
116 and then connected directly to ground so ?ltering of
ance network. Accurate voltage control in these prior
the large A.C. component on the photocathode end could
has been very di?icult to realize since it is in
be realized by means of resistor 1M and this ground con
dit?cult to provide accurate voltage control of
nected capacitor. Likewise, capacitors 166 through 115
power supplies that have large current requirements. In
could be connected directly to ground provided the
addition, these prior systems have not compensated for
capacitance of each is decreased to a value correspond
deviations due to variations of current drawn
ing with the remaining series capacitance. By utilizing
by the individual dynodes.
a ?lter system of this type, the voltage across the ?lter ca
The present invention provides a unique voltage con
trol system which corrects for both variations in supply
voltage as well as variations in current drawn by the
pacitors would be much greater than the individual stage
voltage and consequently capacitor failure would more
readily occur. It can be seen that by employing the
capacitors in series as shown in FIGURE 1 that e?ective
capacitance of the capacitors at the photocathode end is
realized, and yet, the voltage across each of these capaci
tors is limited to a relatively small value as determined by
the muimum peak-topeak voltage of the oscillator
It has been found by employing the above described
dynodes. Voltage control is realized by sensing the volt
age of dynode 131 with respect to ground. It can be
readily seen that when dynode 131 is not drawing current
?lter system, with a ten volt photomultiplier output, the
A.C. component superposed on this ten volt output is only
that this control voltage is the voltage on capacitor 67.
Since the voltage output of oscillator 11, and therefore
the voltage on capacitor 67, would, without the control
system, vary with variations of 13+ voltage, this voltage
control is responsive to variations of B+ voltage. In .
addition, the voltage On dynode 131 will also re?ect
current drawn by this dynode because there is a resultant
about 50 millivolts peak~to-peak, whereas, when the ?lter 45 voltage
drop across resistor 93. Since the voltage of
stage of voltage multiplier 12 is a- con—
to approximately one-half volt peak-to-peak.
secutive integral multiple of the ?rst stage, control of
Capacitors 118 and 119 may be used to provide addi
the ?rst stage will of necessity result in control of the
tional ?ltering and are dependent upon the particular
network is not employed, the A.C. component is increased
photomultiplier employed. The values of these capaci 50
tors may be determined empirically; however, it is to be
understood that they are not critical for effective opera—
tion of the present invention.
It should be particularly noted that power required
by this scheme is virtually only that drawn by the dynodes
and there is therefore no wasted power as is the case in_
remaining stages.
In operation, when dynode 131 draws current, the
voltage drop across resistor 93 causes an amplitude in
crease of the signal from oscillator 11, since the control
system requires that the oscillator maintain the voltage
constant on dynode 131. Due to the multiplication char
acteristics of voltage multiplier 12, the dynodes at the
photocathode end of the photomultiplier will have a
resistance network devices. Since the power consumed
voltage available per stage, and consequently a
is very small it is possible to employ a small 13-]- power
greater multiplication factor than the dynodes at the an
supply and utilize an oscillator and control system as
ode end. This is because the dynodes at the photocath
herein described. In addition, since linearity is poor in 60 ode end draw considerably less current than those at the
resistance network photomultiplier power supplies, to
anode end with resultant smaller voltage drops across
provide control it has been necessary to employ a high
the ?lter resistors in series with the dynodes. The value
impedance divider across the power supply and parallel
of resistor 93 is selected so a nearly flat over-all gain
with the entire resistance network. Since linearity of the
power supply of the present invention is highly stable 65 factor is realized by the photomultiplier during all load
conditions. That is, during large loads the potential dif
under varying loads, voltage control is realized by sam
between dynodes 122 and 123 may be 210 volts
pling a single stage as will hereinafter be more completely
and the potential di?erence between dynodes 13d and
131 may be only 190 volts and during small loads may
The current drawn by the photomultiplier from capaci
201 and 199 volts, respectively. In this manner the
tors 67 through 78 is relatively small and effective con 70 be
over-all photomultiplier gain is maintained at a nearly
trol may be therefore prevented since electrical charge
constant value irrespective of load. Obviously, if only a
would remain on these capacitors particularly during low
voltage and not a current responsive control were em
load operation. That is, if the hereinafter described con
ployed, the over-all multiplication factor would decrease
trol detected the over-all multiplication factor as being
with increased load since the potential difference between
too large, the amplitude of the oscillator output signal
dynodes 12.2; and 123 would be about 200 volts whereas
above'described operation is related to a 200 volt control
would be about 190 ‘volts due to the‘ largevoltage'drop
across resistor 93. For purpose of illustration these abovev
which assumes that oscillator 11 provides at leasta 2G0
p‘eak-to-‘peak voltage output. Obviously if 200 volt'c‘on-v
trol were necessary, the p'eak-to-peak voltage output of
potential: changes 'have been ‘exaggerated and 'in prac
tice are vconsiderably less.
Even without‘?lter resistors
oscillator 11 would’ be‘ selected to have a value consider
ably greater ‘than 200 volts inorder to realize ‘rapid con
trol. ‘It has‘ been found that an oscillator providing a
93 throu‘ghliht?tis ‘desirableto employ'a current respon
sive control to maintain‘ 'a constant multiplication'factor
since each ‘stage of the DC. voltage multiplier has 'a
?niteoutput resistance which can'never be reduced ‘to‘
the selected breakdown voltage of ’zener diode 135. The
the potential‘ ‘difference between "dynodes 13d and ‘131
Control is accomplished by applying thepotential of
maximum peak~to-peak voltage output of about 200 volts,
provides very satisfactory control for‘ dynodeto-dyuode‘
voltages up to about ‘175'v volts.
It is to beunderstood that voltage control from slightly‘
dyno'de' 131 in series with thermistor 133' and vzener'diojde
135' to the base of transistor 27. Thermistor133, zener
diode 135 and capacitor 137 and 13%, which‘shunt zener
readily be obtained by the above described scheme and
lected .to bring about the particular value of photomulti
plier gain desired. These components may be prepack-v
series, B+ power supply, ‘DC. voltage multiplier param
greater than zero volts to many thousand volts may
diode13‘5, ‘are interdependent and zener diode 135 is se 15 may be accomplished merely by- selecting di?’erent oscil
lator parameters; zener diodes ‘or employing several in
aged for particular voltage characteristics and provided
with ‘plug-in ‘connections-13941401 tov realize ease “of se
lection and assembly; ' TlieB+ supply is applied in series 20’
through resistors 143 and 144 to the'base- of. transistor 27
eters, 'etc., and still remain within the scope Of'ihiS'iHVCl'b'
Capacitors 137 and 138 functionas'xa bypass for; the
high frequency noise inherent- in zener diode“ 135' and‘ are
selected to match the particular diode‘ employed. In
addition, the time constant of capacitors 13'? and139j and
the resistance of thermistor 133 'are seleeted "sothe overr
through‘zene'r' diode 135 isfregul‘ated independent of the 25 all feedback loop will operate stably wat a variety of‘oper-*
ating conditions and thereby‘obviatehunting;v
B-'1'- voltage'andfthel operatingpoint of 'zener diode r1351
Since the breakdown‘ voltage-‘characteristic 'of’zener
is‘very accurately determined.“
diode 135 varies directly with'temperature, thermistor
Forrpurpo'seof ‘description, it is assumed that Lzener
133 may be provided in" series therewtih' to'compensate'
diodef=135 hasa breakdown'voltagerof 2001volts: In' addié
and zener- diode3~146 is'selected to‘ have a breakdown volt;
age‘ of a predetermined value which ‘isile'ss'than- the 13+
supply, '11 volts‘, forexamp'le. Therefore, the current‘
tion, transistor 27'is=seleeted to have a very large‘ current'
gain and the base thereof draws’ very little- current when‘
-for this variation. Thermistors have - a negative 'tem-'v
p'e'rature coe?icient‘ and the resistance thereof therefore
conducting‘;~ Upon the application of 13+ ‘power, zener
varies inversely with temperature. The charactristics of
diode 135' offers, in?nite impedance and the‘bas'e of train-I
sister 27 will be driven positive and-into a saturation state;
acteristics of zener diode 135 such that as the break
thermistor 133‘ are selected to inversely match thechar
Since trwsistor27 is saturated, ‘the ‘emitter-collector im-‘ 35 down voltage acrossthe zener diode increases withteme
perature, the resistance and corresponding,voltage'drop’
pedance there'ofzis minimum and maximum B+> voltage
across-thermistor 1'33 decreases by the ‘same amount;
is available'to thebases of transistors 19 and i21',"as shown ‘
T0 illustrate, ifiit is'desired 'to maintaindynode 7131 'at
by-curvesf‘f” and‘ f‘h”fof"FIGURE-"2A. As previously
100 volts, the breakdown voltage of‘ zener diode" 135"
explained, oscillatorxll will then provide maximum volt
age, output. D~.C.'.voltage multiplier 12 .is'very rapidly 40 may be selected at 971/2 volts and the voltage drop‘ across"
thermistor 133 at 21/2 volts, both at room temperature;
charged since it drawsivery little currentand the dynode's
Therefore, when dynode'131. is at 100 volts,‘ 971/2 volts
very rapidly acquire their integer multiple potentials of’
will appear at the anode of zener diede 13,5 and it will’
therefore start conducting. If the temperature would"
greater than 200 volts, zener >diode1135' rapidly» starts con-~
ducting,v When zener diode. 135 conducts, the'curren't 45 rise to'about 35° C., the breakdown voltage of ‘zener
diode 135 would raise to about 98% and the resistance
from the base of transistor is.shun'ted~ through zener diode
of thermistor 133 would decrease so the‘ voltage drop‘
135,. thermistor 133, resistors-93 and‘ 8t)‘ and diodes 42
across the thermistor would be about 11/2 volts‘. There
and 41 toground. Since‘ this’ shunting path providesv a‘
fore, zener diode 135 would again start'conducting when’
much smaller impedance than the path through, transis
dynode 131" was at 100 volts. In this manner the control
tors 27, 19 and 21 and resistor 147 to ground, .the voltage
at the base of transistor 27 very closely approaches ground 50 system provides accurate voltage regulation'independent
of temperature variations. There‘ are other ‘relatively,
when zener’ diode 1355 becomes conducting. Therefore,
minor temperature coef?cie'nts in the power supply and
since the base of transistor. is driven to ground, the col-.
209*ivoltsr When dynode 131 has‘ a voltage very slightly -
oscillator and in practice, thermistor 133 is empirically.
lector-emitter impedance ‘thereof is. ‘rapidly increased '
thereby greatly reducingthe. current available to the bases‘ 55 selected to compensate for these‘ as well as‘ the tem
perature coeihcient of zener diode'135.
of transistors 19 and 21, as shown by curves “f” and “h”
The output ofv the‘ above described system istaken;
of FIGURE 2B. Inactual operation the peak-to-peak
from anode 151 of photomultiplier 13 which is applied"
voltages shown in FIGURElB would approach zero
tothe input of ampli?er 153 which ‘provides a‘volta'ge'
when zener diode 135' conducts; Ifthe voltage on dynode
outputindicative of the rate of bombardment of photo
131 then reduces very slightly below 200 volts, zener
diode 13S becomes non-conducting and the potential ap 60 cathode 120. It is desirable that ampli?er 153 have a'
large input impedance since the anode’ current is relaplied to the base of transistor 27 increases thereby greatly
tively small. This could be accomplished, for example,
reducing the collector-emitter impedance thereof and re
by employed ca‘scaded emitter follower transistors in
sults in large current being applied to the bases of tran
ampli?er 153.
sistors 19 and 21 and thereby providing maximum volt
The following is a tabulation of the values of’ com
age output from oscillator 11 and increasing the voltage
ponents employed in the present invention.‘ It is to be
on dynode 131 back to .200 volts. It should be partic
understood these values are only exemplary and ‘sub
ularly noted that since voltage multiplier 12 draws very
stantial departure therefrom may be made and .still re
little current and transistor 27 has a high base impedance
main wit-hinthc scope of the present invention. For
and: draws very little current, the voltage variation at
example, when the power supply is employed to ‘supply
the base of transistor 27 varies from only about .1 volt
to about ground potential during normal operation. It
high voltage to a source other than a photomultiplier,
can therefore be seen that the response rate of the con~
it may be desirable to change various parameters con~
sidering such factors asv load, voltage requirements, im- trol system is very rapid and maintains voltage multiplier
12 within extremely close tolerances as determined by 75 pedance characteristics, etc. Likewise, substantial de
parture may be made when different photomultiplier
voltages are required.
3. A power supply device comprising a direct current
source operatively connected to the input of control
16 _____________________ _. 20 ohms.
17 ____________________ _. 8 microfarads.
29-40 _________________ _. .01 microfarad.
DC. voltage supply, said D.C. voltage supply compris
ing a diode-capacitor voltage multiplier network having
67-78 _________________ _. .01 microfarad.
80-91 _________________ _. 10 megohms.
93 ____________________ ...
94';- ____________________ _.
95' ____________________ _.
96 ____________________ _.
97 ____________________ _.
98 ____________________ _99 ____________________ _.
100 ___________________ ...
101 ___________________ _.
102 ___________________ _.
103 ___________________ _.
104 ____________________ ,.
105-116 _______________ _.
118-119 _______________ ...
135 ___________________ _. 100 volts.
137-138 _______________ _.
143 ___________________ _.
144 ___________________ ...
146 ___________________ _.
147 ___________________ _.
a plurality of discrete D.C. voltage output stages, said
control means responsive to the voltage at one of said
10 stages for controlling the output current from said con
trol means to maintain the voltage on said stages at
10,000 ohms.
20,000 ohms.
30,000 ohms.
39,000 ohms.
51,000 ohms.
62,000 ohms.
68,000 ohms.
82,000‘ ohms.
91,000 ohms.
100,000 ohms.
110,000 ohms.
120,000 ohms.
.01 microfarad.
.01 microfarad.
133 ___________________ _. 10,000 ohms at room
approximately constant values.
4. A power supply device comprising a direct current
source connected to the collector and base of a transistor,
15 the emitter of said transistor operatively connected to the
input of an oscillator, the output of said oscillator opera
tively connected to the input of a voltage supply having
a plurality of discrete D.C. voltage outputs, one of said
discrete D.C. voltage outputs operatively connected to the
anode of a zener diode, the output of said zener diode op
eratively connected to the base of said transistor, whereby
the voltage at said one of said discrete D.C. voltage outputs
is maintained at the breakdown voltage of said zener diode.
5. The combination of a photomultiplier device and
25 a power supply, said power supply comprising a direct
current source connected to the collector and base of a
.01 microfarad.
13,000 ohms.
43,000 ohms.
transistor, the emitter of said transistor operatively con
nected to the input of an oscillator, the output of said
oscillator operatively connected to the input of a voltage
11 volts.
1,000 ohms.
B-l- ___________________ _. 22-35 volts.
means, the output of said control means operatively
connected to the input of an oscillator, the output of
said oscillator operatively connected to the input of a
supply having a plurality of consecutive stages having
consecutive integral multiple D.C. voltage outputs, each
of said consecutive stages operatively connected to con
In view of the foregoing, it can be seen the present
secutive dynodes of said photomultiplier device, a ?lter
invention provides a small lightweight and highly reliable
network including a plurality of resistors individually con
D.C. high voltage supply. In addition, it is uniquely 35 nected in series between each stage a respective dynode,
adaptable for use in conjunction with a photomultiplier
in that control is a function of 3-]- power, photomulti
one of said dynodes operatively connected to the anode
of a zener diode, the output of said zener diode opera
plier load, and temperature, and therefore maintains a
constant over-all photomultiplier multiplication factor
irrespective of variation of these conditions. Further
tively connected to the base of said transistor, whereby
the voltage on said dynodes are varied as a function of
40 the load of said photomultiplier to maintain a constant
over-all photomultiplier multplication factor irrespective
more, reliability of the individual components is en
hanced since the voltage across each component is main
of load changes of said photomultiplier.
tained at a minimum.
6. The combination of an electron discharge device and
It is to be understood in connection with this inven pp a power supply, said electron discharge device being of
tion that the embodiment shown is only exemplary, and
the electron multiplier type, having at least a plurality
that various modi?cations can be made in construction
of dynodes with secondary electron emitting character
and arrangement within the scope of the invention as
istics and an anode, output means connected to said
de?ned in the appended claims.
anode, said power supply comprising a diode-capacitor
What is claimed is:
multiplier network having a plurality of discrete
l. The combination of a photomultiplier device and 50 D.C. voltage output stages, each of said dynodes of said
a power supply, said power supply comprising a diode
electron discharge device being individually connected to
capacitor voltage multiplier network having a plurality
a separate output stage of said diode-capacitor voltage
multiplier network of said power supply.
impedance, each of said output stages being individually
7. The combination of a photomultiplier device and a
connected to separate dynodes of said photomultiplier 55 power supply, said power supply comprising a diode-ca~
device, whereby the total power required by said power
pacitor voltage multiplier network having a plurality of
supply is about the same as the total power supplied by
discrete D.C. voltage output stages and a low output im
said power supply to said dynodes.
pedance, each of the dynodes of said photomultiplier de~
2. The combination of a photomultiplier device and
vice being individually connected to a separate output
a power supply said power supply comprising a direct 60 stage of said power supply, whereby the total power re
current source operatively connected to an oscillator the
quired by said power supply is about the same as the
output of which is operatively connected to the input of
total power supplied by said power supply to said dynodes.
a D.C. voltage supply, said D.C. voltage supply com
prising a diode-capacitor voltage multiplier network hav
References Cited in the ?le of this patent
of discrete D.C. voltage output stages and a low output
ing a plurality of discrete D.C. voltage output stages and
a low output impedance, each of said output stages being
individually connected to separate dynodes of said photo
multiplier device, whereby the total power required by
said power supply is about the same as the total power
supplied by said power supply to said dynodes.
Oliver _______________ __ Dec. 26,
Felici ________________ __ Mar. 6,
Ford et al. ____________ __ June 2,
Ketchledge ____________ __ vOct. 3,
Seike _______________ .._ Nov. 14,
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