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JPS50152701

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DESCRIPTION JPS50152701
1 Japan Patent Office ? Japanese Patent Application Laid-Open No. 8150-152701?U, ?
specification tF1 method for dual-channel stereo 2 method # 2 + request for combined signal LT
such as NIB, and one having a larger mold width level R and Rb signals and the other of the Rb
and Rf signals and fi [orthogonally-contrast-t] signal reproduction within a range including 1 'in
one synthesized signal ?? orthogonally -1 Stomach! In order to reproduce 1EndPage: 1 within
the range in which these signals are included in the pruning (the number of composite signals,
the selective addition and subtraction of the corresponding signals included in the composite
signal and the RT are performed. In order to form a relative phase by changing the phases of
these synthesized signals, and further, in the signal synthesizing means, one synthetic signal of
the larger one of the amplitude levels whose phase is changed relatively is relatively compared.
Selectively combining with the other composite signal of the smaller amplitude level which has
been carbonized, and each one of the signals Lf * LbtRf and R, b / is different in each of the
output signals from the signal combining means. It is characterized by having appeared as a
signal. 3) Make the R1 and R2 signals nearly orthogonal to one of the Lb and Rb signals, and the
R and R signals. A synthesized signal LT in which the Lf and Lb scratch signals and the other fit'f
are orthogonal to each other. And the Rf signal with the larger amplitude level and the Lb signal
with the smaller amplitude level with the Rf signal with the smaller amplitude level, so that the
R1 signal is approximately orthogonal to one of the Rb oyster Rf signals The other of the R and
R1 signals is fi [orthogonalized to one of the composite signals R to 412 individual signals L +,
Lb, R, and Rb] In reproduction within the range included in the signal, the ratio of the larger
amplitude level to the smaller amplitude level is 0, 9244: 0. In order to selectively add and
subtract the combined signal and the corresponding signals contained in RT as defined in JI 'and
Le H, the phases of these combined signals are changed to form a relative phase, and In the
signal combining means, one of the larger ones of the amplitude levels whose phase is relatively
changed. -Selectively synthesizing the composite signal with the other synthesized signal of the
smaller one of the voice width level relatively changed in phase, to each of l output signals from
the signal synthesizer-a signal и Lf, ' L1) A reference channel stereo signal reproduction method
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characterized in that different one of lR and Rb appears as a dominant signal.
4) Rf and Lb signals with the larger amplitude level, and R2 and Rb signals with the smaller
amplitude level, so that the R signal is tuff orthogonal to one of the above and Lb scratch signals,
and the Rb signal is the above. And the Lb scratch signal, the composite signal LTN that is made
to be fiff orthogonal to the other, and the amplitude level of the R2 and Rb signals of the
amplitude level and the smaller amplitude level, and the Lb scratch signal. The individual signals
Lf, Lb and Rf from the combined signal R0 in which one of the Rb and R2 signals is fiff
orthogonal to one of the Rb signals and the L signal is buried and orthogonal to the other of the
R and R signals And Rb in the range in which these signals are included in the two combined
signals, one smaller amplitude level of the larger amplitude level. The ratio to. In order to
perform selective addition and subtraction of the corresponding signals contained in the
synthesized signals LT and RT, the phases of these synthesized signals are changed to form a
relative phase, and the signal synthesis means And selectively combining one of the combined
signals of the larger amplitude level relatively changed in phase with the other combined signal
of the smaller amplitude level relatively changed in phase; Furthermore, the phase of the output
signal of one of the output signals of the signal combining means may be such that a different
one of the signals Li-sLbtRf and Rb appears as a dominant signal in each of the l output signals
from the combining means, A signal reproduction method O for G-channel stereo, characterized
in that it shifts approximately 900 with respect to the other ? output signals of the signal
synthesis means
Signal reproduction method for channel stereo.
Detailed description of the invention The present invention is a method of recording information
of 1 0 individual channels on a recording medium having only 2 independent channels иии /
EndPage: 2, decoding and reproducing an encoded signal The invention relates to a method of
playing back a da-channel stereo that improves the listener's hearing such that sound comes in
from l individual sound sources, in particular when recording such information and reproducing
it with l unbeakers. It is about The applicant previously proposed such a dual channel stereo
device as Japanese Patent Application No. F8 # 6-391I / Da "Multichannel Information Encoder,
Defender and Recording Medium", or here, for example, a disc record, a tape and a tape, etc.
Kotra stereo recording medium that allows the form of? It is used as a recording medium, and the
signals to be reproduced from the "front left" and "front right" speakers are respectively recorded
along with the channels of the "front left" and "right side" speaker channels, and the phases of
these signals are mutually In the left F-rack, the left rear signal is the same as the left channel
signal, and in the right track, the right rear signal is more advanced than the right front channel
signal. Try to be in phase. Further, in the decoder, 12 fl и outputs from the disc record are
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received from each track one by one, and these ? outputs are appropriately processed by the
scheme circuit and separated into signals similar to 1 individual channels. Each of these
individual channel signals contains, as a dominant signal, the information contained in the voice
channel originally recorded, together with the information from the other channels in attenuated
form, and such signals as l individual signals. Play from the speakers. Recently, there is growing
interest in general multi-channel recording and single playback methods called ?Stereo Adora 7
J (5tereoquadruphonic) J, but after matrix processing of the information of the da-channel, the
co-track is Other methods have also been proposed for recording along with the medium and
decoding to extract the information so as to give the desired hearing of the dachannel
information during playback. Among them, the encoder matrix of the applicant's familiar method
is shown schematically in FIG. Vector diagrams are shown in FIGS. 2 and 3 to illustrate the
operation of the decoder. The encoder matrix in FIG. 1 operates to encode program information
of four individual channels indicated by left front Lf, left 41, Lb1 right rear Rb and right front R2
in one new channel LT and RT. .
Two signals are input terminals respectively. #, 4. r and connecting each of these input terminals
to both of a pair of summing devices @ 10 and 12 ? summing device 10 Fi A matrix consisting
of operational amplifiers and resistors can be used, and the signal Lf can be 0. It is operated to
add 9 co-multiplications, signal Lb'trO09?-doubled, signal Rb multiplied by -o, 3ix times, and
signal R1 multiplied by 0.313. The g summation unit 12 is shown in which these coefficients are
arranged near the connection point of each input terminal of the summation unit @ 10 and the g
summation unit 12 has the same configuration as the summation unit 10, with the signal Lf
multiplied by 0.113 Therefore, the sum of the signal Lb multiplied by -o, 3t3, the signal Rb
multiplied by 0.924I and the signal R2 multiplied by O, de J1 is obtained. ?????? ????
??????????????????????????????? Composite signal taken out
of the summing circuits 10 and 12. And R1 are shown in phase form in FIG. 1 in the form of a
zero composite signal supplied to a converter / converter of a recording apparatus such as 2)
rack magnetic tape recording / separating / stereo recording disc. FIG. 2B represents the
synthesized signal LT supplied to the left recording track, and FIG. 2B represents the synthesized
signal R2 supplied to the right recording track. Here, it is composed of two equal signals Lf and
Lb of the same phase in 0.92 da and one signal of the same length but opposite to each other-o;
3t3--Rb and 0.31JR. Similarly, from nine combined signals RT1, 1 in phase, one larger ? signal,
0, 9? $ R, and 0.9JIIRb and the smaller ? signal in reverse phase with each other ?? 313 Lb
and o, 1t3It Become. Note that 1) General signal, Lb, Rb and Rf are complex program information,
and it is not possible to show the phase relationship in vector representation, but when
considering the relationship of these signals at a single frequency, The display can show the
phase relationship and can illustrate the function of the device. The recorded program with
composite signal, r and R1 can be played back on a conventional stereo playback device, or
EndPage: 3, dematrixed with a special resistance dematrixing network! It can be understood that
its details are not directly relevant to the present invention and will not be discussed hereinafter,
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and in the dematrixed network, the respective dominant signal Lf. To the extent that Lb, Rb and
Rf and the other signals which are attenuated by these dominant signals and ? incidental signals
which are lowered by jclB, are generated.
-As can be understood from the following description, the above-mentioned matrix can be
damaged. For example, consider the operation of the above dematrixing network when supplying
equal signals representing center + front,-and Rt to input terminal 2 and da. ?, JIJ- to JO7, so the
synthetic signal, as long as? New signal five formed 0 to t & i No RT? For the same reason, a new
signal B is formed by extending the length to 8 Jos 7. However, by supplying nine equal signals
Lb and Rb to the input terminals ? and ?, respectively, it is attempted to record the ?oentsrbaok? J signal later; , 313-'0.j4 '/ fold, and a new signal C is formed similarly, and the combined
signal RT is similarly shortened to form a new signal of length o, s + i. Therefore, although it can
be seen that the efficiency of II'i recording differs between the signal supplied to the "rear"
terminal and the signal supplied to the "forward" terminal, this is a fatal defect of the seed matrix
system. In order to improve the characteristics of the above-mentioned 0) matrix IJx, all-pass
phase transition networks 1 and 16 are inserted between the output terminals to produce 1
signal LT1! Form a new set of signals L / T and R / by shifting the relative phase between RT and
RT 900, and A method of supplying / and l (/, to the recording TT device has also been proposed.
Like Jin. By setting the relative phase shift to 90 ', it is possible to improve the reproduction
quality from the above point, but on the other hand, a large distortion occurs otherwise. For
example, if equal input and Rf are supplied to the matrix 2 ии (in the same way as when obtaining
the "front center" signal), as shown in Fig. 3 and Fig. 3B] These signals AI and B1 are out of phase
with each other by 900, so that a blurry and unclear sound image (virtu & 1 image) is
reproduced. Furthermore, the basic problem that the ?rear center? signal is partially offset has
not been solved. In order to obtain a clear sound image for stereo reproduction, it is important to
make the phase of ? signals supplied to the speaker as close as possible to the same phase.
There is a need to be able to relatively uniformly transmit all of the signals applied individually or
jointly to the terminals. The object of the present invention is to eliminate the above-mentioned
drawbacks of the conventional matrix shown in FIG. Another object of the present invention is to
propose a method of improving the matrix-processed signal so as to have an extremely excellent
arrangement, and reproducing the original da-signal from the two synthesized signals obtained
by matrix-processing the da-signal.
In order to achieve such an object, according to the present invention, 1Rf signal is generated
from one of the amplitude level and one of Rb signal and R2 and Rb signal having smaller
amplitude level, and Lb. R1 and R2 of the larger one of the synthesized signals -LT1 and wg
swing amplitude bells such that the Rb signal and the other of the Rb signals are orthogonal to
each other and P1ff orthogonal to the other of the Rb signals. R signal and small amplitude of the
amplitude level, and jb-'hi bl and signal, so that Lf I is orthogonal to one of the Rb and the town
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signal, and Lb signal The other of the Rb and R1 signals is orthogonal to the other of the Rb and
R1 signals. The above-mentioned combined signal L? Can be reproduced per K where Lb, R and
Rb are reproduced within the range where these signals are included in the two combined
signals. And R1 are received, the phase of one of the combined signals is changed relative to the
other phase, and the signals included in the two combined signals are combined into a picture to
produce ? output signals Each of these output signals 1 forms a signal Lt as its dominant signal.
-One of Lb, Rf and Rb, and 1 further taking out the 1 output signals. . ????????????
? The synthesized signal LT handled in the present invention and RT # is can be formed on the
basis of the encoding device 11JK for reference channel stereo according to Japanese Patent
Application No. @ ry-tth I of the present applicant. In this encoding system, it is intended that IJKx make an original original signal into an appropriate phase relationship with an appropriate
all-pass network and then sum and finally obtain two synthesized signals LT and RT. . More
specifically, to minimize the number of all-pass circuits and achieve this purpose, the L and Lb
signal Qll sums are taken twice. -That is, in the first summing network, those obtained by
multiplying each of these signals by 0.92 are added, and in the second summing network, Lf is
multiplied by 0.313. In the third sum total circuit network, a signal obtained by multiplying the
signal Rb by 0.311 and a signal obtained by multiplying the signal Rf by 10 and JIB are added to
the third sum total circuit network. -The first sum total of the outputs of the first and third sum
total networks in the third sum total network after shifting the phase of the first sum signal
output by 1..90 'with respect to the phase of the third sum signal output. Similarly, after shifting
the output of the #th summing network by 900 phases with respect to the output of the second
summing network, the outputs of the second and fourth I summing networks are combined in the
fourth summing network.
Let the outputs of the fifth and fifth summing networks be the combined signals LT and R1
respectively. The above combined signal and R1 are processed according to the present invention
to obtain a reference output-signal: 1 these combined signals all direct In addition to the stereo
speaker system, the AL can also be used for recording on a tape recorder or stereo disc recorder
and later playing on a two-channel stereo device. As described above, by configuring the signal K,
it is possible to improve the phase relationship between the "forward" and "rear" signals as being
symmetrical to the "central" signal. Although it is possible to apply the above encoding technique
when it is desired to make the phase transition between summed signals finally obtained
different from one example, in that case, the same as 4 above. -It is necessary to use a matrix.
However, in this case, according to the present invention in which the ?forward? and ?rear?
symmetrical states are changed, according to the present invention, the reproduction quality can
be improved upon reproduction by a normal stereo system, and moreover, by the dechannel
dematrixing. The reproduction quality of the Ford rough acoustics system can be improved 0 'the invention described with reference to the drawings below 09 Prior to describing the
invention, the above-mentioned features forming the synthetic signals LT and R1 Described is an
encasing equipment for a dual channel stereo system disclosed in F15W-//. First, a preferred
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example of the encoder is shown in FIG. Such an encoder company is very similar to the encoder
described in the Japanese Patent Application No. N-194 I / Society for which the applicant of the
present application is the above-mentioned optical application, but in that it gives a constant
phase transition to No. It is different. Here again, the individual channels of the program
information are named Lf, Lb, Rf and Rb for left front, left rear, right front and right rear,
respectively, and these duchannel signals are input terminals of the encoder, that is, иии, 22 and JK
Both the supplied 0 input terminal / I and ? are connected to a pair of summing devices and to
1 and both input terminals n and y are connected to another pair of summing devices @ 30 and
32. The summing device and the 32 companies have similar configurations, and both operate to
add 0.9211 times each of the two supplied signals. The summing device I and ?? are similarly
configured, but in this case the summing device is that one of two signals multiplied by 0.313 is
added to the other signal multiplied by -0, 3113 respectively. In the case of the summing device
f112I, a signal obtained by multiplying the signal Lf by 0.313 is added to a signal obtained by
multiplying the signal Lb by ?0,313 and in the case of the summing device 30 The signal
multiplied by Rbvt 0.3t3 is added to the signal Rf multiplied by ten and JIB multiplied.
The ~ 32 outputs are fed to the respective summing units to the all pass phase shifting networks
71, 36.31 and V respectively. The network 34I and Qig each shift the phase by (F + de o O), and
the network 36 and ? each shift the phase by и (F + O '). For the angle V, either of these
reference angles. Any choice may be made except that equalizing is required in the case of one
encoder or decoder. (1) Usually, these phase shift angles are lagged, but if the encoder or
decoder treats the phase shift as a phase shift, the above phase shift angle can also be set as a
phase shift. A phase angle difference as shown occurs in the individual phase transition
networks. That is, in the network 3 and in the monk, the signals from the summing devices 1 and
32 cause a phase shift of O o with respect to the signals from the summing devices I and 3?.
The outputs of the phase shifting networks 311 and I are summed at equal proportions in the
summing device # 2 and the sum condition. The phase shift network and the output signal of the
monk are similarly summed in the case of additive summing. The final combined output signals
LT and R1 are taken from the summing device p and the output terminals of the cup and q,
respectively, and these combined output signals are decoded into two signals by the reproduction
method according to the present invention, or It can be supplied directly to the company's stereo
speaker system, or it can be recorded first on a tape recorder or stereo disc recorder and then
played back on a co-channel stereo device. Next, the jFI! Referring to J, FIGS. JA and jB
respectively show the phase relationships of the combined output pressure LT and RT in a vector
diagram. As can be seen from these vector diagrams, the voltage LT is in antiphase with each
other, with one signal 0.9-Da L and 0.9 Koda Lb that are equal in phase, relatively large and
relatively large, or relatively five in magnitude. However, it is composed of two signals 0113Rb
and -0, JIBR, which are smaller and equal in magnitude and have 9000 phase differences with
respect to the signals Itf and Lb. Similarly, signal RT is in-phase and for relatively large .lambda.
Signals 0.9 .lambda. R1 and O ", and for signals R2 and Rb which are in opposite phase to each
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other, but relatively large. 900 which is smaller than the other Q signal 0. JI 3 L, and -o, 5 ts L 1). By giving a phase difference of Oo between the larger signal and the smaller signal in this
manner, the encoder of the above-mentioned IIJi Sha ff-// 9 KoJo can exhibit extremely large
effects. .
и и In other words, considering the case where a forward signal consisting of the signals Rf and Lf
of equal magnitude ? is supplied to the matrix, the synthesized signal is the first! It can be seen
that vector components A and B become as shown by dotted lines in FIG. This result does not
completely satisfy the above-mentioned desired condition of X, which makes these vector
components in phase, but (as in the case of FIG. 3), the corresponding vector components de-O 0
to each other. It can be seen that the force i is improved as compared to the conventional device.
If, at the same time, a backward signal is applied by supplying equally large signals Lb and Rb to
the input terminals ? and ? ? ? ? respectively, the resulting composite signal will have
dotted arrows C and 5b in FIGS. It will be indicated by D. It can be seen that the magnitudes of
the vector components C and D are identical to the magnitudes of the vector components and B
obtained when adding only the "front center" signal. In this way, the ENCO in Fig. 3 (with one
layer is symmetrical to the front and the rear, and it is recommended to improve the central
signal to be in phase with the ? ? ? ░ 1). An important point with respect to the form of the
invention presented is that although the magnitudes of the vector components vs. person and B
are equal, the opposite relative phase states are obtained for the vector components C and D
obtained by adding the "back center" signal. It is. According to this, the "front center" signal and
the "back center" signal can be distinguished clearly in the decoding according to the present
invention, but such an effect can not be obtained by the conventional decoding method. It should
be noted that the reverse of the sign of the summing device 30 does not significantly impair the
operation of the encoder, so that the combined signal LT and the signal when the "front center"
or the "back center" is added are both RT can be completely in phase. Therefore, the encoder
configured as such can not distinguish between the "front center" and "back center" signals
during the decoding process. In the above-mentioned encoder, prior to shifting the phase with
the network 3da, #, 31 and PageEndPage: 6 иии, the summation networks 1, и 30 and 32 sum the
signals Lf, Lb, R1) and Rf However, this makes it possible to construct the circuit economically.
Instead of performing the summing process in this way, it is also possible to sum the appropriate
signals in the required proportions by connecting the summing circuit and the matter after the
#fr individual phase transition networks, for example. it can.
However, if the summation processing is performed first as in the example described above, the
number of phase shift networks required in the encoder can be reduced to one instead of one.
Next, the stereo signal encoded by the encoder shown in FIG. 5 is used as the dominant signal
(each from the two adjacent channels (although the information is mixed and diluted somewhat)).
An example of a decoder apparatus according to the present invention, which is supplied to one
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speaker apparatus by decoding into the included signals, is shown in the figure. Recording a
single synthesized signal LT and RT from a recording eta и medium by means of a suitable
converter (for example KR conventional stereo pickup in the case of a disc record) 1 These
signals are respectively applied to the input terminals y and j of the decoder system. Signaling to
shift the phase of these signals t to be suitable for de-matrixing, and RT respectively with
differential phase shifting networks jlI and! It is assumed that the phase difference between the
signal R and the signal R is 900, as in the above-mentioned Japanese Patent Application No. 43911. Phase shift network The relative position of the two signals obtained by phase shift!
Shown in the vector diagram for the output terminals of da and j ?. These signals are supplied to
each of the l summing devices sr, O O1 ? co and ta, respectively, in the proportions indicated in
the block representing the respective summing device. That is, in the summing device jt, the LT
multiplication signal O, decodared multiplication is added to the signal multiplied by -o, 3ts, and
the summation device 40 adds 0, 924c и LT to 0iIJRT, and summation In the device 4J, 0. JIBL, is
added to 0.9J4 'RT, and in summing device 441-0, 313 LT is added by 0.9 Koda R, K'. Signaling
at such a ratio, and summing R1 k, summing device II, O O1 J J and 1 # output terminals 44. ?
?? 'и 70 and 7 output terminals generate new signals J, /, I, /, 11 /, ? and l /,% as shown in the
vector diagram near each terminal. Do. As can be seen from these vector diagrams, these new
signals are respectively the combination of the dominant signals Lf, Lb, Rb and R2 and the
associated signals from the respective terminals. This is considered to be the preferred method
for forming the Ford Rough Onck signal. On the other hand, as described above, when the sign is
summed in the case of summing in, for example, the summing network X, the sign is small in this
fitting if one of the signals shown in FIG. 31 or 33 is used. Vector component is inverted, for
example, the smaller vector component 0.
??????? Phase of 0.313Rf is reversed. In dematrixing under such conditions, each of the
diluted signals is a combination of the dominant signal 'and two mutually antiphased signals,
such signals being one of the listeners. It is understood that it is not desirable for a person-not a
fi. In the vector diagram of FIG. 5, the sign and phase angle are indicated to each vector
component of the company, but in FIG. 1, the figure is prevented from being obscured and
repeated unnecessarily. In order to avoid the indication, 0-Fi in FIG. 1 which did not use the
above-mentioned display method, after 0 de-matrix processing shown only by the relative
position of the vector component, the output terminal ? t, 41 ░ 70 and It may be required to
make the main components LttLbs "b and Rf appearing in the & lt; & quot; For example, it is
desired that all of these main components be in phase. In order to do that, 1 All output signal
phase transition network lco each. The t data, 14 and itac are provided to cause the networks 16
and 11 to generate a relative phase shift of 0 ░ relative to the other networks 12 and 14I. The
output signals of these phase shifting networks are then amplified by respective gain control
amplifiers 90.92.941 and 96. The gain of these amplifiers is controlled by supplying a control
signal to its control electrode, and the amplified output is further read by the Spy EndPage: 7 car
91. ? ? , 100 and ioi respectively supply. When it is desired to enhance the hearing of the signal
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to be reproduced, the output terminals of the one phase shifters 5trt and St as described in the
Japanese Patent Application No. 6-301911 according to the prior proposal of the present
applicant. The control and switching logic network 10 is responsive to the signal taken out of the
circuit, thereby controlling the gains of the amplifiers 90, 92, 941 and 9 ?. That is, in the control
and switching logic 10, the phase shifter 54! ???? Through the automatic gain control
circuit, the signals appearing at the output terminals of 6 are processed with these signals kept at
a predetermined constant level. These signals are then de-matrixed in a circuit similar to the dematrix circuit formed by summing circuits sr, to, 6- and 61 I, and the sum of the four signals
obtained can be appropriately time constant network The sum signal is fed back to the automatic
gain control circuit so that the sum remains constant.
Output lead @ io da + iot, iot, combined by linear addition and subtraction of the individual
signals. And generate control signals at / 10. In this example, connecting each of these output
conductors to the gain control terminals of amplifier 0, 9 ?, 9 da and 96, increase the gain of the
channel including the main signal instantaneously and decrease the gain of the other channels.
By supplying the control signal to the gain ItIL amplifier in a manner as described above, rf for
each individual independent sound source can obtain perfect hearing. 'If the sound of the
channel named Channel 1 disappears and another sound appears on another channel different
from that, the gain of the first channel is rapidly attenuated and the gain of the other channel is
increased. Thus, the above-mentioned logic time f 1510-acts. Thus, according to the present
invention, it is possible to reproduce the discrete channels at high level. According to the present
invention, it is possible not only to reproduce these channels in a very rich sense of reality, but
also because they are signals or symmetrical, the signal between any two adjacent input terminal
pairs, ie, I, "; 1: -R1, iRb-Rf; R, -L" can be "breaded" to make the level constant during the banning
operation. Furthermore, when playing a record on a conventional two-track stereo device, the
signal to be reproduced is relatively sharp at # 1. Next, FIG. 7 shows another example of the
encoder of the above-mentioned Japanese Patent Application No. f7-// 9? da. Although the
symmetry between the front and back of the signal is changed here, it is preferable to do this
depending on the purpose of use. The general configuration of the encoder in this example is
similar to that of the apparatus of FIG. 4, but the signal combination is different as described
below. Input terminal /// 2. The original input signals of // l // l and // I, L + b, Rb. And R, l
summing devices / 20 * I? cos respectively. 12 and 1 to 26 are supplied at the rates shown as
shown for each summing device. More specifically, signals obtained by summing unit l? co and
respective ones obtained by multiplying 0.313 times and -0, 313 times each of Lb are added, and
signals Lf and Lb are respectively added to summing device l. , Add the octopus sample. Similarly,
the sum of the signals Rb and the doubled signals is added to the summing unit @ / 20, and the
sum of the signals Rb and R2 is multiplied by 0.92 in the summing unit / 24.
Summation unit l?0. / Cok, l? da and l?t output terminals are connected to all pass phase shift
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networks / 21, / 30, / 3 and i3qK, respectively, and the phases of the signals transmitted to these
networks are relatively o6. Nail 0, too and 13j0. In the total-sum unit 13, the outputs of the phase
shift network / core and the output of the third row are added at an equal ratio, and similarly, the
outputs of the phase shift network / 30 and / 34 t in the sum total / unit 31. Are added in equal
proportions. Adder / 34 and / 31F output terminals / '10 and / 4J6C appearing synthetic signals
and RT respectively J) Rack custom-made on magnetic tape or stereo disc record and then with
stereo device It is possible to reproduce or de-matrix these combined signals into an overhead
signal as described above according to the invention. A vector diagram is shown based on a
geometrical signal system consisting of such synthesized signals, and the vector diagram of R1
consisting of axes denoted by EndPage: 8, и 3c, 900 and 100 etc. The phase is drawn with respect
to a virtual electrical axis named "oo axis". That is, in FIG. 1, the signal 0.313Rb which has
received the phase shift V with the minimum of rom is shown as being coincident with 0 / axis,
and the signal 06 with a relative phase delay of 900, . It shows 1900 behind JIJRb. The kernel
signal 0, 924 ILb is geometrically 1 0 relative to the O 0 axis. Similarly, in FIG. JB, the signal
0.313L that has received the phase shift of V + Ge 50 is arranged offset from the 0 ? axis by da j
0, and the signal O with a relative phase delay of + oo. , Takohiro-Rft-vector component 0.310 Lf,
delayed by 900. @ This signal 0, 9 cos 4 IR f is geometrical and makes 22S 4 ░ with respect to
the O 0 axis. One of the important advantages of the matrix of FIG. 7 is shown below. A "front
center" signal is added to the matrix by supplying equal signals Lf and R2 to terminals 11- and //
I respectively. As can be seen from FIG. 1, in this case, the signals Ly # i-1 DEG 0.9-D, and -0, 31
JR are formed, thereby forming vector component lines indicated by dotted lines. It can be seen
that this component Fie exactly matches the scientific 900 axis. At the same time, the synthesized
signal RT shown in FIG. TB is 0.94! A vector component B, which is composed of Rf and 0.3IIL, is
shown by the dotted line.
The magnitude of this vector component B is l, and this component B also matches the
geometrical 900 axis exactly. Thus, the two signal components occurring at the output terminals
I and O are equal in magnitude and in phase, so that an accurate and clear central signal can be
reproduced. However, the provision of the state m occurs if the back center signal is added to the
matrix by supplying equal magnitude M ? Lb and Rb equal magnitudes to the input terminals //
'I and ll ?. In this case, the output signal LT shown in FIG. JA is composed of 0.9?4ILb and 0.31
? R5, and forms a composite signal LT # i vector component O, which coincides with the
geometrical axis of 41j '. Do. On the other hand, the combined signal R1L r rBmK indicates a yoke
4C10, 924! ??????? ???? Composed of Lb, this composite signal R1 forms a vector
component, the magnitude of which is the same as component C, but in this case coincides with
the geometry-axis of / 330. As is apparent from FIG. 1, the vector components C and D mutually
form a 900, and as described above, it can be seen that a distorted sound image is produced in
stereo reproduction. Thus, although the encoder of FIG. 7 can obtain a sound image that is a
shaky sound when applying the "front center" signal, if the "back center" signal is applied, ifi can
be obtained. . This proves to be a very desirable way to distinguish the front from the rear when
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reproducing the signal in a co-speaker stereo device. In each case, the vector components people
= BtO and D all have the same amplitude of l, so the strengths of the front center and rear center
signals are equal, which is also desirable -9. Next, the present invention reproduction method for
decoding the signal encoded by the encoder of FIG. 7 is supplied with the combined signal and
RT to l and 16 respectively, and further an all-over phase transition circuit is provided. Through
net / III and ljO to give relative phase shift of aso between synthesized signals. By combining one
signal vector component with each other by this phase shift action and setting it as an
appropriate phase position, de-matrix processing of these synthesized signals is performed. The
vector diagrams of the synthesized signals LT and R1 corresponding to FIGS. 7A and zB,
respectively, are again drawn beside the input terminals / 41 and / 4'4 to aid in the description.
However, the delay phase angle and the sign are omitted here for the sake of clarity.
A vector diagram of the signals L 'and R / obtained after passing through the all-pass phase
shifting networks lda and ljO is illustrated in connection with the output terminals of the
respective phase shifting networks lda and ljO. These signals L / and RtT are dematrixed by
supplying l summing networks ts?, iso, ist and 131, respectively, at the rate indicated in the
circle representing the summing device. EndPage: 9 of the summing device: similar, whereby
each output terminal / 60 of the summing device 15 to ljt, / ? 2. The signals including FL
signals LftLb * Rb and R2 as dominant signals are taken out from / 44I and / 44 respectively. A
vector diagram of these l signals is illustrated in connection with each output terminal, but as can
be seen from these betator diagrams, each dominant signal component is combined with one
incidental signal component from an adjacent channel, Similar to the example of the decoder of
FIG. B, connect the output terminal of the dematrixer network of FIG. IA9 to the additional phase
shift network, and as described for the apparatus of FIG. 6, the relative phase position of the
main components to the desired position It can also be done. The additional phase shifting
networks described above can be mounted as desired, but such networks can be further
connected to corresponding gain control amplifiers to provide signals to each speaker and the
amplifiers Can also be controlled by logic and switching networks, as described in the example of
FIG. 7 and U.S. Pat. No. 4-30191. и If the encoding or matrix circuit disclosed in the abovementioned patent-application is refined as described above based on the encoder of the abovementioned Japanese Patent Application No. F7-// 9 Koda, reproduction when recording medium
is reproduced with a stereo device The quality can be improved and, at the same time, the
reproduction quality can be improved when reproducing with the da-channel de-matrix quad 7
onic device. The reason for the latter improvement is described in the encoding matrix described
above! This is because there is no ambiguity in the sense of directionality inherent in trufflers.
That is, in the conventional circuit of FIG. 1, there is an ambiguity in the sense of direction
localization, and it is not clearly determined whether the encoded signal is generated from either
the front or rear speaker pair. When considering the phase relationship of the matrix in Fig. 1,
vague points in the sense of direction localization tend to occur in at least two points, and in fact,
in the ? passage from the left rear speaker to the right rear speaker There is a continuous wide
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area of ambiguity extending along.
In other words, it sounds like the sound and voice panning between the input terminals
corresponding to these speakers transition from the left rear speaker to the left front speaker,
then transferred to the right front speaker, and then transferred to the right rear speaker .
According to the above-mentioned matrix, there is no such ambiguity in the sense of directional
localization.
4. Brief description of the drawings. FIG. 1 is a block diagram showing the structure 6 of the
conventional encoder matrix, FIG. 2B, FIG. 2B, FIG. 35 and FIG. FIG. 4 is a block diagram showing
an example of the configuration of an encoding matrix according to the present invention. 11
and tB are vector diagrams for illustrating the operation of the circuit of FIG. 1, and FIG. 11
shows an example of the configuration of a decoder apparatus according to the present invention
for decoding a signal recorded by the encoder of FIG. FIG. 7 is a block diagram showing a
modification of the encoder of FIG. 4. FIG. 7 is a vector diagram for explaining the operation of
the encoder of FIG. 7. FIG. 9 is a block diagram showing operations of the encoder of FIG. FIG. 6
is a block diagram of a portion of the re-master according to the invention for decoding the
recorded signal with the illustrated encoder. C, 4c, ?, l ... input terminal, 101/2 ... summing
device IS / I, #, ... all-pass phase transition network, IItX) t22s2 g ... ... input terminal, tE * 30t 32
иии Summation device, 3. ! ??????? l) ииииииииииииииииииииииии и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и
и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и и ? и и и Input terminal, j 4 ', j 4 и и и Phase
transition network, str, to, ? 2 ░ 6 и и и Sum unit, 66 * tie 70 + 7-и и и Output terminal, 12. 11 I, It,
It... All-pass phase transition network, 90.92, 9 da, 9 ?. Gain control amplifier-, 9 ff, 99 ░ / DO,
10 / .. loudspeaker, 10-.. control and switching Logic circuit, 104I, 104.101. 10 иии Output
conductor / / / / / / / / / / и и / / 1 и и и Input terminal, l? O1 / JJ, / Jl, / J4 и и и и и и и и и / 21, / 30, /
32. / 314... All-pass phase transition network, IJ &, / 31... Summing device, too, t octopus...
Output terminal, 14I data t / 4'6... Input terminal, / III, /! 0... All pass phase transition network, /
3 [lambda], is ,, tit, ist... / ? 2 ░ / 4 #, / 44 ... output terminal. ????????????
?????? Tufts, 4J7 Ei, 5 Afhi 5 B no jry, 15 ? ? 177 5.7 End Page: 11 f 7 i 5 .. 5 ? + 1 1
specification (2) Drawing 1 Wen & Hair Inventors other than the above, patent applicants or
agents (1) Inventors (1) 2) One person EndPage:
??
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