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JPS549901

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DESCRIPTION JPS549901
??? Description 1, title of the invention
Sound image localization control device
3. Detailed Description of the Invention The present invention relates to a sound image
localization control apparatus for controlling a sound image in any direction of 360 ░ by a 4channel signal. In order to improve the performance effect etc. in recent years, the sound image
is controlled to an arbitrary direction of 360 by means of a 4-channel signal, for example, fixed at
a fixed position or continuously moved. Conventionally, in such a device, the signal of the sound
source is generally distributed to the signal of four channels by panpot solium, and the signal of
this four channel is converted by the encoder into a funnel and transmitted by a general stereo
transmission system. ing. However, such a mechanism has a problem that the complicated pan
pot of the mechanism requires a lithium and an encoder, and the structure becomes complicated.
The present invention has been made in view of the above-mentioned circumstances and is
capable of moving a sound image without using a pan pot volume, an encoder or the like, or
changing the moving speed of the sound image to fix the sound image at a desired position. It is
an object of the present invention to provide a localization control device. A simple example of
the present invention will be described below with reference to FIGS. 1 to 4. In general, a fourchannel signal encoded is represented by the following equation 1). EndPage: 1, but LT is the L
channel encode signal RTidlt channel encode signal S has an audio signal ? with a right center
RC of 08 and substitutes an arbitrary value for ? in equation (1) in the counterclockwise
direction. The graph shown in FIG. 1 is obtained. In FIG. 1, RC is at the right center, CF is at the
front center, Lc is at the left center, and BC is at the rear center. Therefore, a signal satisfying the
graph of FIG. 1 can be obtained by always providing a 90 ░ phase difference between the L
channel encoded signal LT and the R channel encoded signal RT. FIG. 2 is a block diagram of an
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apparatus for obtaining encoded signals LT and RTt of L-R channels having a phase difference of
90 ░. That is, the audio signal is modulated by the carrier (CG) from the carrier generator CG by
the modulator (first multiplier) MLI, and if necessary, it is converted to a sine wave through the
band-pass filter FL, and the demodulator (second The third multi-slayers are given to ML, ML. On
the other hand, the phase of the output of the carrier generator CG is controlled with respect to
the modulation carrier by the phase shifter Ps, and the demodulation carriers having a phase
difference of 90.degree. The signal is supplied to the third multiplier to obtain encoded signals
LT and RT of the respective 1 JIL and LR channels.
KB is a key date that converts the phase shift amount of the phase shifter ps. Here, the
modulation carrier is eel?t, one demodulation carrier is eos (?1 + 6), the other demodulation
carrier is eol (?t + (?+ 2)), the AM wave is FI (t), and the modulation wave is M. If it is set as (1),
following 2) Formula will be obtained. Fl (t) = M, (t) и eom ?t и song 2) and one demodulation
carrier F ? (1) = c, (?t + #), then the demodulated low frequency i signal is ) Is shown. Fa (t) =
Mo (t) co-? иии 3) If the other demodulation carrier is Fs (t) = com (?1 + (?10?)), the low
frequency signal demodulated is the following 4 ) Is shown. Fa (t) = Mo (c) cos (? ?-) = Mo (t)
sin 6??4) Therefore, low frequency demodulated by controlling the phase ? with respect to
the modulation carrier of the above 3), 4) equation The magnitude of the signal can be
controlled. The change in magnitude of this low frequency signal is proportional to eoll or cos
(.theta .-)-), and 1) is satisfied. FIG. 3 is a block diagram showing an example of the phase shifter
PS, in which the phase ? is controlled in a digital manner. The above block diagram will be
described below with reference to the time chart of FIG. That is, the output (FIG. 4 a) of the basic
signal generator BG is divided by 1 / n by the counter CTI, and this divided output is divided into
a pair of 7 ring 70 FF *, FFt clock manual powers CL, CL, give. Then, the pair of flip flops F1
double, FFa Q1 (FIG. 4 b), b ((fourth block и) output is the other flip flop Ds, Da large input giving
each output Q1 Q1 (4 th FIJ c '), A signal which is out of phase by 90 ░ from Q * (FIG. 4d) and Q
* respectively is taken out and applied to a 4-person digital multiplexer MX. Note that the pair of
flits f70 and fFF1. The phase of the FF ? is 90 ░ out of phase with each other by 7t Q1, and the
Qm output is taken out as a demodulation carrier. It is an oscillator that oscillates 10,000 OS # i,
a signal having a sufficiently long period compared to the oscillation period of the basic signal
generator BG, and a fourteenth preset counter that counts the output of the PT + charger
oscillator O8. When the low frequency output level is fixed at one foot level according to the
control mode of sound image localization specified by the first preset counter PTI and the third
preset counter PTsu key date KB described later, a constant count value is held. When the low
frequency output level is to be changed with time, the output of the oscillator O 8 is counted, and
the count value is changed with time to be ?.
Then, the first preset value EndPage: 2 the count value of the reset counter PT + counts the
output of the reference signal generator BG, and the second preset counter PT! Hegriset value is
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given and given. The carry signal of the first preset counter PTt is counted by a 2-bit third reset
counter PT, and the digital multiplexer MX designates a signal to be selected according to the
count output. The output of each of the first first and second free-lag flops FFI and FFt, Qt, Ql, Qt,
and Q are sequentially selected by the digital multiplexer MX. The signal selected by the digital
multiplexer MX is applied to the NOR terminal and the D1 terminal of the flip-flop FFs. The
output (FIG. 4f) of the NOR gate NG is the second reset counter PT !. System is enabled). When
the second preset counter PT3 receives a high level signal from the NOR (NG), the second preset
counter PT3 stops the count operation and presets the count value of the first preset counter
PTs. Further, when the second reset counter PTt receives a low level signal from the above N0 fl
"-ING, it is permitted to count the output z4 pulse of the reference signal generator BG in the
down mode and is lowered from the above preset value. Count. When this count value becomes
O, the carry (FIG. 4 g) is output and the free-lag flop FF! Give to the clock CL. Therefore, when the
output of the digital multiplexer MX is low level, the output of the flip flop FF (FIG. 4h) is inverted
at the rising edge of the carry to become low level, whereby the output of N0In '-NG is Become.
Therefore, the output of Flip 70 Tsuso FF, is the second! In synchronization with the rising edge
of the carry output of the reset counter PT2, when the output of the multiplexer MX is low level,
it is inverted and becomes low level. Meanwhile the second! ??????????? The reset
value is controlled by the first reset counter PTs, and the rise / fall timing of the output of the
free-lag flop FF is controlled by the preset value, that is, the flip-flop FF *, the output Q * of FFt,
Ql, Qt, It is possible to control the phase relative to Q. Therefore, by using the output of the flipflop FFs as a modulation carrier, a modulation carrier having a desired position difference with
respect to the demodulation carrier can be obtained relative to the demodulation carrier.
In the above embodiment, the phase shift of the carrier is controlled digitally, but may of course
be controlled in an analog manner. As described above in detail, according to the present
invention, the audio signal is modulated by the carrier signal 2 and this modulated wave is
separately filled with the demodulated carrier signal which is in the two-phase relationship
orthogonal to the carrier signal. Since the channel's channel code signals LT and RTt are
obtained, it is possible to provide a sound image localization control apparatus capable of
accurately controlling the sound image localization with a simple configuration.
4, Brief description of the drawings 3, -1 Fig. 1 is a graph for explaining the present invention,
Fig. 2 is n. A block diagram showing one embodiment of the present invention, FIG. 3 is a block
diagram showing the phase shifter of the above embodiment, and FIG. 4 is a time chart
explaining the operation of the phase shifter. CG: carrier generator, ML,... Modulator, ps: phase
shifter, ML,-demodulator, ML,... Demodulator 0 applicant agent patent attorney Takehiko Suzue
EndPage: 3; Knee / [: i year 2 figure heat и 3 figure EndPage: ?
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